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LM1881N Datasheet(PDF) 5 Page - National Semiconductor (TI) |
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LM1881N Datasheet(HTML) 5 Page - National Semiconductor (TI) |
5 / 12 page Application Notes (Continued) COMPOSITE SYNC OUTPUT The composite sync output, Figure 1(b), is simply a repro- duction of the signal waveform below the composite video black level, with the video completely removed. This is ob- tained by clamping the video signal sync tips to 1.5V DC at Pin 2 and using a comparator threshold set just above this voltage to strip the sync signal, which is then buffered out to Pin 1. The threshold separation from the clamped sync tip is nominally 70 mV which means that for the minimum input level of 0.5V (p-p), the clipping level is close to the halfway point on the sync pulse amplitude (shown by the dashed line on Figure 1(a). This threshold separation is independent of the signal amplitude, therefore, for a 2V (p-p) input the clipping level occurs at 11% of the sync pulse amplitude. The charging current for the input coupling capacitor is 0.8 mA, Normally the signal source for the LM1881 is assumed to be clean and relatively noise-free, but some sources may have excessive video peaking, causing high frequency video and chroma components to extend below the black level refer- ence. Some video discs keep the chroma burst pulse present throughout the vertical blanking period so that the burst actually appears on the sync tips for three line periods instead of at black level. A clean composite sync signal can be generated from these sources by filtering the input signal. When the source impedance is low, typically 75 Ω, a 620Ω resistor in series with the source and a 510 pF capacitor to ground will form a low pass filter with a corner frequency of 500 kHz. This bandwidth is more than sufficient to pass the sync pulse portion of the waveform; however, any subcarrier content in the signal will be attenuated by almost 18 dB, effectively taking it below the comparator threshold. Filtering will also help if the source is contaminated with thermal noise. The output waveforms will become delayed from be- tween 40 ns to as much as 200 ns due to this filter. This much delay will not usually be significant but it does contrib- ute to the sync delay produced by any additional signal processing. Since the original video may also undergo pro- cessing, the need for time delay correction will depend on the total system, not just the sync stripper. VERTICAL SYNC OUTPUT A vertical sync output is derived by internally integrating the composite sync waveform (Figure 2). To understand the generation of the vertical sync pulse, refer to the lower left hand section Figure 2. Note that there are two comparators in the section. One comparator has an internally generated voltage reference called V 1 going to one of its inputs. The other comparator has an internally generated voltage refer- ence called V 2 going to one of its inputs. Both comparators have a common input at their noninverting input coming from the internal integrator. The internal integrator is used for integrating the composite sync signal. This signal comes from the input side of the composite sync buffer and are positive going sync pulses. The capacitor to the integrator is internal to the LM1881. The capacitor charge current is set by the value of the external resistor R SET. The output of the integrator is going to be at a low voltage during the normal horizontal lines because the integrator has a very short time to charge the capacitor, which is during the horizontal sync period. The equalization pulses will keep the output voltage of the integrator at about the same level, below the V 1. During the vertical sync period the narrow going positive pulses shown in Figure 1 is called the serration pulse. The wide negative portion of the vertical sync period is called the vertical sync pulse. At the start of the vertical sync period, before the first Serration pulse occurs, the integrator now charges the capacitor to a much higher voltage. At the first serration pulse the integrator output should be between V 1 and V 2. This would give a high level at the output of the comparator with V 1 as one of its inputs. This high is clocked into the “D” flip-flop by the falling edge of the serration pulse (remember the sync signal is inverted in this section of the LM1881). The “Q” output of the “D” flip-flop goes through the OR gate, and sets the R/S flip-flop. The output of the R/S flip-flop enables the internal oscillator and also clocks the ODD/EVEN “D” flip-flop. The ODD/EVEN field pulse opera- tion is covered in the next section. The output of the oscilla- tor goes to a divide by 8 circuit, thus resetting the R/S flip-flop after 8 cycles of the oscillator. The frequency of the oscillator is established by the internal capacitor going to the oscillator and the external R SET. The “Q” output of the R/S flip-flop goes to pin 3 and is the actual vertical sync output of the LM1881. By clocking the “D” flip-flop at the start of the first serration pulse means that the vertical sync output pulse starts at this point in time and lasts for eight cycles of the internal oscillator as shown in Figure 1. How R SET affects the integrator and the internal oscillator is shown under the Typical Performance Characteristics. The first graph is “R SET Value Selection vs Vertical Serration Pulse Separation”. For this graph to be valid, the vertical sync pulse should last for at least 85% of the horizontal half line (47% of a full horizontal line). A vertical sync pulse from any standard should meet this requirement; both NTSC and PAL do meet this requirement (the serration pulse is the remainder of the period, 10% to 15% of the horizontal half line). Remember this pulse is a positive pulse at the integra- tor but negative in Figure 1. This graph shows how long it takes the integrator to charge its internal capacitor above V 1. With R SET too large the charging current of the integrator will be too small to charge the capacitor above V 1, thus there will be no vertical synch output pulse. As mentioned above, R SET also sets the frequency of the internal oscillator. If the oscil- lator runs too fast its eight cycles will be shorter than the vertical sync portion of the composite sync. Under this con- dition another vertical sync pulse can be generated on one of the later serration pulse after the divide by 8 circuit resets the R/S flip-flop. The first graph also shows the minimum R SET necessary to prevent a double vertical pulse, assuming that the serration pulses last for only three full horizontal line periods (six serration pulses for NTSC). The actual pulse width of the vertical sync pulse is shown in the “Vertical Pulse Width vs R SET” graph. Using NTSC as an example, lets see how these two graphs relate to each other. The Horizontal line is 64 µs long, or 32 µs for a horizontal half line. Now round this off to 30 µs. In the “R SET Value Selection vs Vertical Serration Pulse Separation” graph the minimum resistor value for 30 µs serration pulse separation is about 550 k Ω. Going to the “Vertical Pulse Width vs R SET” graph one can see that 550 k Ω gives a vertical pulse width of about 180 µs, the total time for the vertical sync period of NTSC (3 horizontal lines). A 550 k Ω will set the internal oscillator to a frequency such that eight cycles gives a time of 180 µs, just long enough to prevent a double vertical sync pulse at the vertical sync output of the LM1881. The LM1881 also generates a default vertical sync pulse when the vertical sync period is unusually long and has no serration pulses. With a very long vertical sync time the integrator has time to charge its internal capacitor above the voltage level V 2. Since there is no falling edge at the end of a serration pulse to clock the “D” flip-flop, the only high signal going to the OR gate is from the default comparator when output of the integrator reaches V 2. At this time the R/S www.national.com 5 |
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