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AD-03 Datasheet(PDF) 2 Page - National Semiconductor (TI) |
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AD-03 Datasheet(HTML) 2 Page - National Semiconductor (TI) |
2 / 4 page http://www.national.com 2 The Effects of Non-zero Aperture Time For the analysis of aperture time we will assume ζ to be 0. This is the case of no aperture jitter. We will, however, consider the effects of Ψ ≠ δ. The error (as compared to an ideal sampling process) will then be < f, Ψ > – < f, d > This is equivalent to < f, ( Ψ – δ) >. To progress we must now make some assumptions about the nature of Ψ. If we consider the physical process of sampling that takes place within a sample-and hold amplifier we can make an educated guess as to the shape of Ψ. Consider the sample-and hold circuit shown in Figure 2. When the switch is closed, VOUT takes the form of the equation below: Figure 2: Simplified Sample-And-Hold Circuit The RC time constant of this circuit will be proportional to the aperture time. This implies that Ψ has the form indicated below: To get an idea of what effect this has on the sampling process we will expand f as a Taylor series expansion about the sampling instant: t. Once again we will consider the first two terms of the expansion: Now we can examine the value of < f, ( Ψ – δ) >. < f, δ > is by definition f(t0) and the other terms of the expansion do not contribute to the result. Since Ψ has been normalized, < f(t0),Ψ > is f(t0): the ideal result of the sampling event. If we consider the next term: f'(t0) (t-t0) this is a constant slope going through 0 at the sampling point. This, expanded out gives us an approximation of the error generated by the non-zero sampling time. This implies that the error generated is proportional to the slew rate of the input, multiplied by the aperture time. This result is very similar to the result for aperture jitter. Let us now look at the shape of Ψ that might be expected in a CCD or SAW device where the sample consists of the charge deposited in a bin as the bin passes beneath an input terminal. In this case, due to the symmetry of the sampling process, we can expect Ψ to be an even function: such as a gaussian, or a rectangular pulse then the odd nature of (t-t0) will force < f'(t0) (t-t0),Ψ > = 0. Now in order to determine the error generated by the non-zero sampling time we must consider the next term in the Taylor series expansion. Now the expected error is: If the input function f(t) is sinusoidal in nature, all of it’s derivatives have approximately equal values so the major difference between this case and the previous case comes in the comparison of < t, Ψ > and 1/2 < t2,Ψ >. How to Minimize Aperture Induced Errors As we have seen in the preceding analysis the results of both aperture time and aperture jitter is an error signal which increases in amplitude as the slew rates at the input terminal of the A/D increase. One set of strategies that are used to reduce aperture errors therefore focus on minimizing this input slew rate. In fact, from an aperture error standpoint the only thing that is important is that the slew rate be small at the instant that the converter is sampling the input, rapid slewing between samples does not contribute to aperture error. Another tack that can be taken to minimize aperture related errors is one which takes advantage of the fact that the noise generated through aperture effects has a random characteristic and therefore lends itself to reduction through some standard signal processing techniques. Reducing the Input Slew Rate In some cases, the input slew rate is higher than it needs to be to recover the information content of the signal to be digitized. An example would be if an input signal were being digitally down converted through aliasing. As an example if a 100kHz signal, modulated on a 101MHz carrier is to be digitized, then there are several possible approaches: 1) Demodulate the signal and digitize the 100kHz base band signal at a rate of 1MHz. This scheme results in very low input slew rates and would be the preferred method from an aperture error standpoint. 2) Digitize the modulated signal at a 1MHz rate, allowing aliasing to perform the down conversion. In this method the usual mixers are eliminated and the digitized signal is identical to that obtained in method 1 above. The problem is that the input slew rates seen by the converter are over one thousand times greater than those seen in the above example and aperture related errors may dominate. Vt V e d out in t RC t () = () − −∞ ∫ ττ τ Vout R C Vin Vin ψψ =< = > e , t0 0, t0 t RC ft ft f' t t 00 () ≈ ()+− () f t error = f' t te dt s 00 t RC 0 () () −∞ ∫ ft ft f' t t t f" t tt 2 00 0 0 0 2 () ≈ ()+ () − ()+ () − () f t error f' t 2 tt , Y s 0 0 0 2 () ≈ () <− () > |
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